Soft Switched Ac Link Buck Boost Converter
Anand Balakrishnan Hamid A. Toliyat William C. Alexander
Student Member, IEEE Fellow, IEEE Member, IEEE
Advanced Electrical Machines and Power Electronics Laboratory Ideal Power Converters, Inc.
Department of Electrical & Computer Engineering Austin, TX
Texas A&M University Phone: 512-***-****
College Station, TX 77843-3128 Email: abpm3u@r.postjobfree.com
Phone: 979-***-****
Email: abpm3u@r.postjobfree.com
Abstract- A novel soft switching high frequency link converter
for medium and high power ac-ac and ac-dc applications is
proposed. The proposed topology overcomes the shortcomings of
conventional dc and ac link schemes and uses 12 bidirectional
switches for a three phase to three phase configuration. An
inductor-capacitor pair with low reactive rating forms the link.
Switches turn on at zero voltage and their turn offs are
capacitance buffered, resulting in low switching losses. Phase
currents are synthesized using precisely controlled current pulses,
which also allows for any desired input or output voltage or power
Fig. 1: Schematic of proposed topology
factor. The converter can perform buck and boost operations in
forward and reverse directions. The proposed topology promises
switches specifically designed for high frequency applications
size, weight and cost reduction while offering improved
are becoming available. The use of resonant circuits in high
performance compared to existing converters.
frequency dc-dc converters has since been reported [7].
I. INTRODUCTION Ac-ac and dc-ac converters employing high frequency ac
links have also been reported [8]-[12]. Most of these converters
Variable frequency drives typically have employed dc
are designed for specific type of source/loads. Reference [1]
voltage or current links for power distribution between the
reported a topology that provided one-step bidirectional power
input and output converters and as a means to temporarily store
conversion for different kinds of loads/sources. This
energy. The dc link based power conversion systems have
configuration used twelve bidirectional switches and employed
several inherent limitations. One of the important limitations is
Pulse Density Modulation (PDM) as a means to control the
the high switching loss and high device stress which occur
currents. The use of PDM reduces the system response because
during switching intervals. This severely reduces the practical
of usage of integral pulses of currents. Topologies that make
switching frequencies. Additionally, while the cost, size, and
use of twelve unidirectional switches, by providing a dc offset
weight of the basic voltage sourced PWM drive is attractive,
to the dc link, have also been suggested. Reference [13]
difficulties with input harmonics, output dV/dt and
proposes a topology with twelve unidirectional switches,
overvoltage, EMI/RFI, tripping with voltage sags, and other
without the dc offset. However, it is limited in operation
problems significantly diminish the economic competiveness
response due to its inability to supply output current at low
of these drives. Add-ons are available to mitigate these
voltages or power factors, at link frequencies sufficiently high
problems, but may result in doubling or tripling the total costs
to avoid input/output filter resonances. Also, there is a large
and losses, with accompanying large increases in volume and
dead time due to the resonant 'fly back' which reduces the
weight.
power capability by about 30%. This largely negates its
High frequency ac link converters have been suggested as an
advantage of using a lower numbers of switches compared to
improved alternative. A high-frequency link allows the
the proposed topology.
flexibility of adjusting the link voltage to meet the individual
In this paper, a new soft switching ac link converter that
needs of the source and load sides and at the same time
overcomes the aforementioned drawbacks while offering
provides isolation between the two [1]. High frequency link
superior control and significant economic advantage is
converters improve the speed of response, and if the frequency
proposed. It consists of 12 bidirectional switches and an ac link
is outside the audible range, reduce acoustic noise [2]. High
composed of a low reactive rating inductor-capacitor pair. The
frequency link power conversion has been employed very
link is charged via high frequency current pulses from the
successfully in dc-dc converters [3]-[6]. This demonstrated the
inputs. The link so charged discharges into the outputs in a
advantages and also the difficulties in working with high
similar fashion. The current pulses are precisely modulated
frequency links. Problems were associated with circuit
such that when filtered, they achieve unity power factor at the
topologies and also device capabilities. With increase in
input while also meeting the reference output currents.
demand and with advancements in semiconductor technology,
Fig. 2: Block diagram to show how the input reference is derived
Filtering is done by low-cost, low-loss and light weight
capacitors. Inputs never directly connect to the outputs and
hence there is inherent isolation between the two, which avoids
any common mode voltage and enables grounding of both
input and output neutral points. Full I/O galvanic isolation may
be provided by a split winding version of the link inductor.
Symmetrical arrangement of the power circuit also provides
fully regenerative operation together with buck-boost
capability. Simulation results are presented to back up the
proposed topology. A 15 kW prototype is presently under
construction.
II. PRINCIPLE OF OPERATION
The proposed soft switching bidirectional ac link converter is
shown in Fig. 1. It consists of two full bridge circuits
composed of reverse blocking bidirectional switches, a link
composed of low reactive rating inductance and capacitance,
and the filter capacitors.
The converter operates by charging the link from the inputs
and then discharging the stored energy to the output. The Fig. 3: Typical waveforms illustrating the operating principles of the
converter is fed with the output current references. The link is proposed converter
charged to an amount which makes the discharging current
exactly meet these references. Since charging and discharging may also be achieved if desired.
take place separately, an estimate of how much the link needs
to be charged to supply the output correctly is required. The Modes of Operation:
controller handles this by translating the output references to Each link cycle is divided into 16 modes, with 8 power transfer
input references. The input reference is derived by the simple modes and 8 partial resonant modes taking place alternatively.
equation that Fig. 3 shows the important current and voltage waveforms over
one link cycle. For a 15 kW, 460 V converters the link
Input Power = Output Power + Losses. (1) oscillates at about 10 kHz. Power is transferred twice during
each link cycle. This is roughly at 20 kHz, thereby resulting in
Fig. 2 shows a block diagram of how the system works. superior control and lesser filtering requirements. Zero voltage
RMS value of the output reference current is used to determine turn-on and capacitance buffered turn-off enables operation at
the RMS of the input current for an ideal converter. A loss this frequency. Medium voltage converters employing this
component is added to this from the loss estimator to get the topology are expected to have a link frequency of about 2.5
exact input command. The instantaneous value of the output kHz.
reference commands could be phase shifted with respect to the There are three basic operations taking place through the 16
output voltages as the load demands. Normally, the modes: energizing, partial resonance, & de-energizing. Modes
instantaneous values of the input current commands are in 2, 4, 6, 8, 10, 12, 14 and 16 are the partial resonant modes and
phase or are phase adjusted with respect to the input voltages as evident from Fig. 3, they make up only a very small fraction
so as to achieve unity power factor, but non-unity power factor of the link cycle time. The link is energized from the inputs
during modes 1, 3, 9 and 11 and is de-energized to the outputs
during modes 5, 7, 13 and 15. The various operating modes are
explained below and their respective circuits are given in Fig. 4
and Fig. 5.
Mode 1 (Energizing): The link is connected to the input
voltage pair having the highest voltage via switches which
charge it in the positive direction. For the waveforms shown in
Fig. 3, the link is connected to input phase pair BC through
switches S3i and S2i. The link charges till Ibi averaged over
cycle time, meets its reference value calculated from (1). The
switches are then turned off.
Mode 2 (Partial resonance): The link capacitance acts as a
buffer across the switches during turn off. This results in low
turn off losses. All switches remain turned off and the link
resonates till its voltage becomes equal to that of the input
phase pair having the second highest voltage. This is the phase
pair the link charges next from. In the example shown in Fig. 3,
the link resonates till the link voltage becomes equal to Vaci.
Mode 3 (Energizing): Switches are turned on to allow the
link to continue charging in the positive direction from the
input phase pair having the second highest voltage. At the end
of mode 2, the link voltage equals the voltage of this phase
pair. Hence at the instant of turn on, the voltage across the
corresponding switches is zero. This implies that the turn on
occurs at zero voltage as the switches transition from reverse to
forward bias. In the example in Fig. 3, the link charges till Ici
averaged over cycle time, meets its reference value calculated
from (1). The switches are then turned off.
Mode 4 (Partial resonance): During this mode the link is
allowed to swing to one of the output line voltages. The sum of
the output reference currents at any instant is zero. One of them
is the highest in magnitude and of one polarity while the two
lower ones are of the other polarity. The converter uses this
simple property to avoid any resonant swing back in the link.
The charged link transfers power to the output by discharging
into two output phase pairs. The two phase pairs are the one
formed by the phase having the highest reference current and
the second highest reference current, and the one formed by the
phase having the highest reference current and the lowest
reference current, where the references are sorted as highest,
second highest and lowest in terms of magnitude alone. For
example, if Iao=10 A, Ibo=-7 A and Ico=-3 are the three output
reference currents then phase pairs AB and AC are chosen to
transfer power to the output. If Vab_o and Vac_o are the
instantaneous voltages across these phases and Vlink is the link
voltage, the phase pair whose voltage has minimum difference
with respect to Vlink is chosen as the first one to discharge to.
For example if Vlink=500 V, Vab_o=400 V and Vac_o=300 V, AB
is chosen as the first phase pair to discharge to.
Mode 5 (De-energizing): The output switches are turned on
at zero voltage to allow the link to discharge to the chosen
phase pair till the output current averaged over the cycle equals Fig. 4: Operating modes 1 to 8
the reference value of the lower phase.
Mode 6 (Partial resonance): All switches are turned off and
the link is allowed to swing to the voltage of the other output
phase pair chosen during Mode 4. For the example discussed
before, the link voltage swings from Vaco to Vbco. This is also
illustrated in Fig. 3.
Mode 7 (De-energizing): During mode 7, the link discharges
to the selected output phase pair till there is just sufficient
energy left in the link for it to swing to the input phase pair
having the highest voltage. When the losses are determined
accurately, this would mean that the output references are
accurately met. Any deviation from this is detected and the
losses re-estimated to eliminate this error.
Mode 8 (Partial resonance): The link swings to the input
phase pair having the highest voltage to be ready to charge the
link in the reverse direction.
Modes 9 through 16 are similar to modes 1 through 8, except
that the link charges and discharges in the reverse direction.
For this, the complimentary switch in each leg is switched
when compared to the ones switched during modes 1 through
8. This is seen comparing Fig. 4 and Fig. 5.
It is observed that the input is never directly connected to the
output resulting in proper isolation between the two. Fully
galvanic isolation can be achieved by using an isolation
transformer in place of the link inductor. It can also be
observed that the converter can operate without that link
capacitor. However, since the topology is tolerant to such
capacitance, a low cost, light weight, and efficient link inductor
with high parasitic capacitance can be used. The inductor being
used in a 15 kW three phase prototype weighs less than 5 Kg,
with less than 3 Kg for the input line reactance, as compared to
over 70 Kg for the input and output filters alone for a 15 kW
VS-PWM drive required to produce comparable low harmonics
on the input and output. Additional capacitance may be
advantageously added to buffer turn-off losses, with the
optimal link capacitance determined by balancing reduced
turn-off losses against the resulting slight decrease in power
throughput.
It must be noted as important that the current pulses are
precisely modulated so that they are sinusoidal when filtered
via the LC filters. Even slightly improper modulation triggers
off ringing in the LC filters which should be avoided. One
situation where there is ringing in the LC filters in spite of
proper modulation of the current pulses is when the voltage of
two phases cross each other. This situation is illustrated in Fig.
6. At the crossovers, the order of charging from the input
phases reverses. The result is that the current pulse from the
increasing phase is advanced whereas that from the decreasing
phase is delayed. This causes the respective phase voltages to
deviate from being sinusoidal and this triggers off small
ringing in the filters. To avoid this problem, the controller uses
a predictive algorithm to detect crossovers and draws a small
Fig. 5: Operating modes 9 to 16
Fig. 7: Input Currents
Fig. 8: Link current and voltage
Fig. 6: Required correction at voltage crossovers
Fig. 9: Input and output voltages phase shifted to demonstrate isolation
between input and output
percentage of extra charge from the decreasing phase. The
correction and its effect are illustrated in Fig. 6.
III. SIMULATION RESULTS
Simulations were carried out for a 15 kW converter with
unity power factor load. Both input and output were at three
phase at 460 V. The link capacitance was 0.2 F and the link
inductance was 140 H. Input current ripple with a 1500 Hz
filter as shown in Fig. 7 is so small as to be almost
imperceptible. The link voltage and current waveforms are
shown in Fig. 8. Fig. 9 demonstrates the ability of the converter
to operate with differing input and output common mode
levels. Input and output voltages are phase shifted by about 50o
Fig. 10: Circuit board and link inductor of prototype under construction
in Fig. 9. Fig. 10 shows the circuit board and the link inductor
of the 15 kW prototype under construction. Fig. 11 shows the
schematic used for simulation.
Fig. 11: Schematic used for simulation
Specialists, pp. 20-26.
IV. CONCLUSION
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